• 专利附录
  • 专利说明
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    • 专利摘要:
    An apparatus and method for controlling the coercive current of a three-phase alternating-current motor is provided for improving the inertia of the current control unit at the lowermost part of the motor control apparatus when the motor is rotating at a high speed. And a three-phase-to-synchronous conversion section, wherein the current control value of the speed control section ) Q axis current command value ( ) And the q-axis current ( ), The d-axis current command value ( ) To correct the corrected d-axis current command value ( Current command value correcting means for correcting the d-axis current command value ) And the d-axis current ( And the eighth mixing means for mixing the three-phase AC electric motor and the eighth mixing means for mixing the current command value ) Q axis current command value ( ) And the q-axis current Axis currents to the error of the q-axis current by multiplying the error of the detected q-axis current by a predetermined gain and a predetermined frequency to obtain a transient d-axis current command value ), Detecting the transient state d-axis current command value ( ) D axis current command value (
    公开号:KR19990070998A
    申请号:KR1019980006197
    申请日:1998-02-26
    公开日:1999-09-15
    发明作者:최종우
    申请人:이종수；엘지산전 주식회사；
    IPC主号:
    专利说明:

    Accelerating current control device and method for three-phase alternating current motor
    [11] The present invention relates to current control of an alternating current motor including a synchronous motor and an induction motor. More particularly, the present invention relates to a three-phase alternating current And more particularly, to an apparatus and method for controlling an induced current of an electric motor.
    [12] The motor control unit is a system that controls the motor to generate the commanded torque, to rotate at the commanded speed or to operate at the commanded position. To this end, a current controller, a speed controller and a position controller are incorporated.
    [13] Among them, the current controller is the basic controller of the motor control device. In the present industry, hysteresis controller, periodic coordinate PI controller, synchronous coordinate PI controller, and state feedback controller are applied.
    [14] Currently, the synchronous coordinate system current controller is widely applied to the high performance variable speed AC motor drive system.
    [15] The PI controller that performs the current control in the synchronous coordinate system, the 2-variable state feedback controller, and the multivariable state feedback controller belong to the synchronous coordinate system current controller.
    [16] The advantage of the current controller in the synchronous coordinate system is that it is convenient to control and has excellent performance since the fundamental wave component of the phase current being controlled is converted into the amount of DC current.
    [17] One of the common features of these controllers is that the d axis and q axis of the synchronous coordinate system are controlled independently of each other.
    [18] Recent trends are that the terms related to the cross coupling and the back-electromotive force of the motor in the synchronous coordinate system are treated as disturbances and compensated proactively, followed by d-q non-interference control.
    [19] Among these, the method which receives the spotlight as a high-performance current controller in the industry is a synchronous coordinate PI controller that compensates the back-EMF component.
    [20] Hereinafter, a conventional three-phase ac current control apparatus and method will be described with reference to the accompanying drawings.
    [21] FIG. 1 is a diagram showing a control configuration of a general motor drive system, in which a speed command of a scalar component ) And the speed of the scalar component fed back ( A first mixer 10 for mixing the first mixer 10 and the second mixer 10, ) And the speed of the scalar component fed back ( ) According to the deviation between the input speed command ) Of the vector component for controlling to rotate at the same speed as the current command value (20) for outputting a current command value (hereinafter referred to as " vector component ") of the vector component output from the speed control section ) And the current of the fed back vector component ( ) To compensate for the difference between the voltage command value of the vector component A current controller 30 for controlling the current controller 30 to output a voltage command value of the vector component output from the current controller 30 ), The voltage command value of the vector component ( (Hereinafter referred to as " PWM ") unit 40 for generating a voltage command value (hereinafter referred to as " And a motor 50 for generating a predetermined current according to the predetermined torque to change the rotation speed.
    [22] FIG. 2 is a view showing a synchronous coordinate system PI current control apparatus in which a counter electromotive force component of the current control unit of FIG. 1 is compensated. ) To feed back the q-axis current ( ) And the d-axis current (Not shown) for converting the current command value of the speed control unit 20 into a three- ) Q axis current command value ( ) And the q-axis current ( And a second mixing unit 31 for mixing the q-axis current command value ) And the q-axis current A q-axis PI control unit 32 for controlling a deviation between the q-axis voltage compensation circuit and the q-axis voltage compensation circuit, A q-axis feedforward compensation unit 33 for outputting the q-axis feedforward compensator 33 a signal of the q-axis PI control unit 32 and a q- ) Are mixed and the resulting q-axis voltage ( A third mixer 34 for outputting a current command value ) D axis current command value ( ) And the d-axis current ( And a fourth mixing unit 35 for mixing the d-axis current command value ) And the d-axis current A d-axis PI control unit 36 for controlling a deviation between the d-axis voltage compensation signal and the d- A d-axis direction compensation unit 37 for outputting the d-axis PI control unit 36 and a d-axis direction compensation unit 37, ) Are mixed and the d-axis voltage ( A fifth mixer 38 for outputting a q-axis voltage ) Of the fifth mixer 38 and the d-axis voltage ( ) Of the vector component including the three-phase signal to the voltage command value ( And a synchronous-three-phase converting unit (not shown) for outputting the converted signal.
    [23] Here, the q and d current command values ( ) ( Is a value given from an upper control section of the current control section 2, and is generally a q-axis current command value ( ) Is the output of the speed control unit 20, and the d-axis current command value ( ) Is the output of the magnetic flux controller in the case of an induction motor and is normally zero in the case of a synchronous motor.
    [24] An apparatus and method for controlling an accelerating current of a three-phase AC motor according to the related art will now be described in detail with reference to the accompanying drawings.
    [25] First, the first mixer 10 receives the scalar component speed command ( And the speed of the scalar component fed back from the motor 50 ) And outputs a resultant signal.
    [26] Then, the speed controller 20 receives the speed command of the scalar component mixed in the first mixer 10 And the speed of the scalar component fed back from the motor 50 ) According to the deviation between the input speed command ) Of the vector component for controlling to rotate at the same speed as the current command value ).
    [27] Accordingly, the current controller 30 outputs the current command value of the vector component output from the speed controller 20 ) Of the vector component fed back from the motor (50) ) To compensate for the difference between the voltage command value of the vector component .
    [28] That is, the three-phase-synchronous conversion unit (not shown) in the current control unit 30 outputs the output current of the motor 50 ) To feed back the q-axis current ( ) And the d-axis current ) And outputs it.
    [29] The output current of the motor 50 ) Is a three-phase signal ( , , ).
    [30] Then, the second mixer 31 mixes the current command value of the speed controller 20 ) Q axis current command value ( ) And the q-axis current ( ) And outputs a resultant signal.
    [31] Accordingly, the q-axis PI control unit 32 controls the q-axis current command value ) And the q-axis current ) And outputs a signal corresponding thereto.
    [32] The q-axis deflection compensating unit 33 includes a q-axis deflection compensating signal for removing the counter electromotive force term and the mutual interference component of the q-axis voltage circuit ).
    [33] Accordingly, the third mixing unit 34 mixes the signal of the q-axis PI control unit 32 and the forward compensation signal of the q-axis directional compensation unit 33 ), And the q-axis voltage of the q-axis voltage circuit and the q-axis voltage from which the mutual interference component is removed ).
    [34] In addition, the fourth mixer 35 mixes the current command value of the speed controller 20 ) D axis current command value ( ) And the d-axis current ( ) And outputs a resultant signal.
    [35] The d-axis PI control unit 36 then compares the d-axis current command value ) And the d-axis current ) And outputs a signal corresponding thereto.
    [36] The d-axis deflection compensating unit 37 includes a d-axis deflection compensating signal for eliminating a counter electromotive force term and a mutual interference component of the d- ).
    [37] Accordingly, the fifth mixer 38 mixes the voltage command value of the d-axis PI controller 36 and the forward compensation signal of the d-axis deflection compensator 37 ) And the d-axis voltage (d-axis voltage) of the d-axis voltage circuit and the d-axis voltage ).
    [38] The q-axis deflection compensation unit 33 and the d-side deflection compensation unit 37 perform non-interference control for independently controlling the q-axis and the d-axis by deflecting the counter electromotive force component and the dq mutual interference component of the motor 50 And also to reduce the burden on the q-axis and d-axis PI control units 32 and 36.
    [39] Then, the synchronous-three-phase converter (not shown) converts the q-axis voltage of the third mixer 35 ) Of the fifth mixer 38 and the d-axis voltage ( ) Of the synchronous coordinate system of the three-phase signal to the voltage command value ( ) And outputs it.
    [40] Accordingly, the PWM unit 40 outputs the voltage command value of the vector component output from the current control unit 30 ), The voltage command value of the vector component ( ) And outputs it.
    [41] Then, the motor 50 outputs the scalar component voltage command value ( And a predetermined torque is generated to vary the rotation speed.
    [42] Then, the rotational speed of the motor 50 is controlled by a current ) And speed ) To repeat the above-described process so that the input speed command ( ).
    [43] The synchronous coordinate PI current controller 30, which compensates the counter electromotive force, can be similarly applied to the synchronous motor and the induction motor. The parameters of the motor used in the application are shown in Table 1 below.
    [44] Induction motor Synchronous motor resistance( ) inductance( ) q axis counter electromotive force ( ) d axis counter electromotive force ( ) 0
    [45] First, the voltage equations for the general synchronous coordinate system q-axis and d-axis of a three-phase balanced AC motor such as an induction motor and a synchronous motor are as shown in Equations (1) and (2).
    [46]
    [47]
    [48] In this case, most of the counter electromotive force in the steady state is concentrated on the q-axis of the synchronous coordinate system because the rotor flux is located only in the d-axis of the synchronous coordinate system.
    [49] From Equation (1), the rate of increase of the q-axis current with respect to time can be expressed by Equation (3).
    [50]
    [51] In Equation (3), the q-axis control voltage is limited by the voltage limitation condition of the inverter (PWM unit in this case), as shown in Equation (4).
    [52]
    [53] Here, the d-axis voltage is as shown in Equation (5) in a steady state.
    [54]
    [55] Here, since most of the counter electromotive force of the AC motor is caught in the q-axis of the synchronous coordinate system of .
    [56] Therefore, the limiting condition of the q-axis control voltage of Equation (4) can be approximated as shown in Equation (6) below.
    [57]
    [58] Further, the rate of increase of the q-axis current with respect to time can be modified as shown in Equation (7).
    [59]
    [60] Here, the synchronous coordinate system q-axis effective counter electromotive force ( ) Is as shown in the following equation (8).
    [61]
    [62] From Equation (7), the minimum time for the variation of the q-axis current can be obtained as follows.
    [63] First, when the current decreases ) Is expressed by the following equation (9).
    [64]
    [65] In addition, when the current increases ) Is given by the following equation (10).
    [66]
    [67] From Equations (9) and (10), the following can be deduced.
    [68] if The q-axis current changes slowly in the positive direction due to the lack of the control voltage, and the negative q-axis current changes in the q-axis direction in the negative direction Effective counter-electromotive force can help to reduce the current, which can decrease rapidly.
    [69] Also if Is negative, the q-axis current changes slowly in the negative direction and decreases rapidly in the positive direction since the q-axis effective counter-electromotive force in the synchronous coordinate system increases to a negative value.
    [70] This phenomenon The smaller the value of.
    [71] Therefore, the conventional adaptive current control device of the three-phase AC motor according to the prior art is designed without considering the voltage limitation condition of the inverter, and in the case of the inverter, the voltage that can be outputted is determined according to the magnitude of the DC link voltage. If it is designed assuming an infinite output voltage with an infinite DC link voltage, the back EMF component of the motor increases at high speed. If the magnitude of the back electromotive force component is similar to that of the control voltage, .
    [72] SUMMARY OF THE INVENTION Accordingly, the present invention has been made keeping in mind the above problems occurring in the prior art, and it is an object of the present invention to provide a three-phase alternating-current motor in which an accelerating current control The purpose of the device is to provide.
    [73] It is another object of the present invention to provide a method of controlling an AC current of a three-phase AC motor corresponding to the above-described apparatus.
    [1] 1 is a diagram showing a control configuration of a general motor drive system
    [2] FIG. 2 is a view showing a synchronous coordinate system PI current control apparatus in which a counter electromotive force component in the current control section of FIG. 1 is compensated;
    [3] 3 is a view showing an apparatus for controlling the coercive current of a three-phase AC motor according to the present invention.
    [4] Figure 4 is a flow chart
    [5] DESCRIPTION OF THE REFERENCE NUMERALS
    [6] 110: current command value correcting unit 120: sixth mixing unit
    [7] 130: q-axis PI control unit 140: q-axis deflection compensation unit
    [8] 150: seventh mixing section 160: eighth mixing section
    [9] 170: d-axis PI control unit 180: d-axis deflection compensation unit
    [10] 190: ninth mixing section
    [74] According to another aspect of the present invention, there is provided an accelerating current control apparatus for a three-phase alternating-current motor including a speed control unit and a three-phase synchronous conversion unit, The current command value of the speed control section ) Q axis current command value ( ) And the q-axis current ( ), The d-axis current command value ( ) To correct the corrected d-axis current command value ( Current command value correcting means for correcting the d-axis current command value ) And the d-axis current ( And an eighth mixing means for mixing the first and second mixing means.
    [75] According to another aspect of the present invention, there is provided a method of controlling an AC current of a three-phase AC motor, ) Q axis current command value ( ) And the q-axis current ) Is detected to detect the error of the q-axis current, and the error of the detected q-axis current is multiplied by a predetermined gain and a predetermined frequency to obtain a transient d-axis current command value ) And then outputs the detected transient state d-axis current command value ( ) D axis current command value ( ).
    [76] DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS Hereinafter, preferred embodiments of an apparatus and method for controlling a coercive current of a three-phase AC motor according to the present invention will be described with reference to the accompanying drawings.
    [77] The general motor drive system to which the present invention is applied is the same as that of FIG. 1, so that the description of the components will be omitted.
    [78] 3 is a view showing an apparatus for controlling the coercive current of a three-phase AC motor according to the present invention, ) To feed back the q-axis current ( ) And the d-axis current (Not shown) for converting the current command value of the speed control unit 20 into a three-phase-synchronous signal ) Q axis current command value ( ) And the q-axis current ( ), The d-axis current command value ( ) To correct the corrected d-axis current command value ( A current command value correcting unit 110 for correcting the current command value of the speed control unit 20 bypassed by the current command value correcting unit 110 ) Q axis current command value ( ) And the q-axis current ( A second mixer 120 for mixing the q-axis current command value ) And the q-axis current A q-axis PI control unit 130 for controlling a deviation between the q-axis voltage compensation signal and the q-axis direction compensation signal A q-axis deflection compensation unit 140 for outputting a q-axis deflection compensator 140 and a q-axis deflection compensator 140, ) Are mixed and the resulting q-axis voltage ( A d-axis current command value (d) corrected by the current command value correction unit 110 ) And the d-axis current ( And an eighth mixing unit 160 for mixing the corrected d-axis current command value ) And the d-axis current A d-axis PI control unit 170 for controlling a deviation between the d-axis voltage compensation signal and the d- A d-axis direction compensation unit 180 for outputting a signal of the d-axis directional compensation unit 180 and a signal of the d-axis PI control unit 170, ) Are mixed and the d-axis voltage ( A ninth mixer 190 for outputting a q-axis voltage ) Of the ninth mixing unit 190 and the d-axis voltage ( ) Of the vector component including the three-phase signal to the voltage command value ( And a synchronous-three-phase converting unit (not shown) for outputting the converted signal.
    [79] The current command value correcting unit 110 corrects the current command value of the speed control unit 20 ) Q axis current command value ( ) And the q-axis current ( ), The d-axis current command value ( And a tenth mixing unit 111 for mixing a predetermined gain K and a predetermined frequency K with a signal mixed in the tenth mixing unit 111, A multiplier 112 for multiplying the amplitude of the signal multiplied by the multiplier 112 and a transient d-axis current command value A limiter 113 for outputting a transient state d axis current command value And the current command value of the speed control unit 20 ) D axis current command value ( ) To obtain a corrected d-axis current command value ( And an eleventh mixing section 114 for outputting the mixed signal.
    [80] 4 is a flow chart of Fig.
    [81] An apparatus and method for controlling an accelerating current of a three-phase AC motor according to the present invention will now be described in detail with reference to the accompanying drawings.
    [82] First, the problems of the conventional current control technique are summarized. The rate of increase of the current is slowed in a sufficiently large region of the speed, and the rate of decrease of the current is large in the region of a sufficiently large negative value of the speed. As shown.
    [83]
    [84]
    [85]
    [86] Here, in the case of the equations (12) and (13), the current control decreases the responsiveness due to the insufficient control voltage.
    [87] Therefore, it can be seen that a new algorithm is needed for fast current control in this section.
    [88] The general synchronous coordinate system q-axis voltage equation of the AC motor is as shown in the following Equation (14).
    [89]
    [90] In Equation 14, since the counter-electromotive force is a function of the normal speed and the magnetic flux and they can not suddenly fluctuate within the current control period, only the synchronous coordinate system d axis current can be used to improve the transient response of the synchronous coordinate system q- Able to know.
    [91] here , If the d-axis current of the synchronous coordinate system is controlled to be lower than the steady state value in the transient state, the q-axis effective counter electromotive force in the synchronous coordinate system decreases, and the current control of the q-axis of the synchronous coordinate system is possible.
    [92] together , It is not necessary to use the current of the synchronous coordinate system d-axis because the synchronous coordinate system q-axis effective counter electromotive force helps the current control of the synchronous coordinate system q-axis.
    [93] Furthermore, the d-axis current of the synchronous coordinate system larger than the rated value increases the effective counter electromotive force of the q-axis of the synchronous coordinate system, so that the control unit can lose the current control capability.
    [94] Therefore, in the present invention, in order to reduce the d-axis current in the transient state, the transient d-axis current command value ). As shown in FIG. 3, it is configured as a function of the q-axis current error and the speed in the synchronous coordinate system.
    [95] Hereinafter, an apparatus and method for controlling the coercive current of a three-phase AC motor according to the present invention will be described in detail with reference to the accompanying drawings.
    [96] First, a three-phase-synchronous conversion unit (not shown) converts the output current of the motor 50 ) To feed back the q-axis current ( ) And the d-axis current ) And outputs it.
    [97] Then, the current command value correction unit 110 sets the current command value of the speed control unit 20 ) Q axis current command value ( ) And the q-axis current ( ), The d-axis current command value ( ) To correct the corrected d-axis current command value ( ).
    [98] That is, the tenth mixer 111 in the current command value corrector 110 sets the current command value of the speed controller 20 ) Q axis current command value ( ) And the q-axis current ( ), The d-axis current command value ( ) To calculate a q-axis current error and output a resultant signal (S1).
    [99] Here, the q-axis current error is calculated by the following equation (15).
    [100]
    [101] The multiplier 112 multiplies the signal mixed in the tenth mixer 111 by a predetermined gain K and a predetermined frequency ) And outputs the transient d-axis current command value ( ) (S2).
    [102] Here, the predetermined gain K is a positive value and the d-axis current command value ) Is excited.
    [103] That is, when the value of the predetermined gain K is large, the transient state is set to a large transient state d-axis current command value ).
    [104] In addition, since the degradation of the current control due to the lack of the control voltage is conspicuous at a high speed with a large back electromotive force, the back electromotive force hardly appears at a low speed, so it is necessary to use the frequency information for the use of the synchronous coordinate system d axis current.
    [105] In other words, in the low speed range where the back electromotive force is small, it is necessary to suppress the fluctuation of the d axis current in the synchronous coordinate system and activate the synchronous coordinate d axis in the high speed range where the back electromotive force is high.
    [106] To do this, the d-axis current command value ) Was generated by the product of the q-axis current error and frequency.
    [107] Here, the transient state d axis current command value ( ) Is calculated by the following expression (16).
    [108]
    [109] Accordingly, the limiting unit 113 limits the amplitude of the signal multiplied by the multiplier 112 and outputs the transient d-axis current command value i · e * ds_t.
    [110] If the transient state d-axis current instruction value i e * ds_t is negative, the limiting unit 113 can increase the effective q-axis counter-electromotive force of the synchronous coordinate system to make the current control difficult, (i · e * ds_t) is set to zero.
    [111] Also, in order to limit the amplitude of the current, the upper limit value of the transient d-axis current command value (i e * ds_t) is also limited as shown in the following Equation (17).
    [112]
    [113] Here, I max denotes a maximum allowable current value of the inverter, i eqs denotes a feedback q-axis current, and i e * ds denotes a d-axis current command value of the current value (i * s ) of the speed control unit.
    [114] The eleventh mixing section 114 mixes the transient state d-axis current instruction value i · e * ds_t outputted from the limiting section 113 and the d-axis current I * ds of the current instruction value i * s of the speed control section 20, And outputs the corrected d-axis current command value i · e * ds_m by mixing the command value (i e * ds ).
    [115] That is, the eleventh mixing section 114 searches for whether the limited signal in the limiting section 112 is larger than "0", and if the transient state d-axis current instruction value (i e * ds_t) 0 "in a more mathematical modify the d-axis current command value (i e * ds_m) as shown in equation 19 is less current command value (i * s) of the speed control unit (20) the d-axis current command value (i e * ds are outputted (S3, S4).
    [116]
    [117]
    [118] If the limited signal in the limiting section 112 is greater than the search result transient state d-axis current instruction value (i e * ds_t) is "0", the eleventh mixing section 114 outputs Transient state d axis The current command value (i e * ds_t) is the transient state The upper limit value of the d axis current command value (S5).
    [119] That is, the eleventh mixing section 114 determines that the transient state d-axis current instruction value (i e * ds_t) exceeds the upper limit value of the transient state d-axis current instruction value (I e * ds ) of the current command value (i * s ) of the speed controller 20 as shown in the following equation (21), the transient state d axis current command value i e * ds_t ) To the corrected d-axis current command value i e * ds_m (S6).
    [120]
    [121]
    [122] The eleventh mixing unit 114 may be configured such that the limited signal in the limiting unit 112 is the upper limit d axis current command value i e * ds_t of the transient state d axis current command value as shown in Equation (20) ), The corrected d-axis current command value i e * ds_m as shown in the following equation (22) (S7).
    [123]
    [124] Accordingly, the sixth mixer 120 mixes the q-axis current command value (i e * qs ) of the current command value (i * s ) of the speed control unit 20 bypassed by the current command value correction unit 110 with the q- Mixes the q-axis currents (i eqs ) of the phase-to-phase converter and outputs the resultant signal.
    [125] Here, the actual d-axis current to follow a normal state the d-axis current command value (E e * ds) transients d-axis current command value (i e * ds_t) modifying the d-axis current command value (i e * ds_m) by limiting the in do.
    [126] In this state, the q-axis PI controller 130 controls the deviation between the q-axis current command value (i e * qs ) and the q-axis current (i eqs ) mixed in the second mixer 120, Output.
    [127] The q-axis deflection compensation unit 140 outputs a q-axis deflection compensation signal (E eqs + E L s i eds ) for eliminating a counter electromotive force term and a mutual interference component of the q-axis voltage circuit.
    [128] The seventh mixing unit 150 mixes the signal of the q-axis PI control unit 130 and the forward compensation signal E eqs + o e L s i eds of the q-axis directional compensation unit 140, And outputs a voltage (V eqs ).
    [129] The eighth mixing unit 160 mixes the d-axis current command value i e * ds_m corrected by the current command value correction unit 110 with the d-axis current i eds of the 3-phase-to- And outputs a result signal.
    [130] The d-axis PI control unit 170 controls the deviation between the corrected d-axis current instruction value i e * ds_m and the d-axis current i eds mixed in the eighth mixer 160 and outputs a signal corresponding thereto do.
    [131] The d-axis deflection compensation unit 180 outputs a d-axis deflection compensation signal (E eds -ω e L s i eqs ) for eliminating a counter electromotive force term and a mutual interference component of the d-axis voltage circuit.
    [132] Accordingly, the ninth mixing unit 190 mixes the signal of the d-axis PI control unit 170 with the directional compensation signal E eds -ω e L s i eqs of the d-axis directional compensation unit 180, And outputs the axial voltage V eds .
    [133] The synchronous-3 phase converter (not shown) converts the synchronous coordinate system signal of the d-axis voltage (V eqs ) of the q- th voltage (V eqs ) of the ninth mixer (190) (V * S ) of the vector component including the signal and outputs the converted voltage.
    [134] As described above, in the apparatus and method for controlling the coercive current of the three-phase AC motor according to the present invention, when the motor rotates at a high speed, the speed control of the current control unit at the lowermost part of the motor control apparatus is improved, There is an effect that a better current control part can be ensured in the high-speed region where the back electromotive force is large, particularly in the region.
    权利要求:
    Claims (7)
    [1" claim-type="Currently amended] A speed control unit and a three-phase synchronous conversion unit, comprising:
    By modifying the d-axis current command value (i * qs) according to the synchronous conversion portion q-axis current (i eqs) - q-axis current command value (i * qs) and the three-phase current command value (i * s) of the speed control unit A current command value correcting means for outputting a corrected d-axis current command value (i e * ds_m);
    And eighth mixing means for mixing the corrected d-axis current instruction value (i e * ds_m) and the d-axis current (i eqs ) of the 3-phase-to-synchronous conversion unit by the current command value correcting means Speed AC motor.
    [2" claim-type="Currently amended] The method according to claim 1,
    The current command value correcting means
    (I e * ds ) according to the q-axis current instruction value (i e * qa ) of the current instruction value (i * s ) of the speed control section and the q-axis current (i eqs ) of the three- A tenth mixer for mixing and outputting a q-axis current error;
    (K) and a predetermined frequency (K) are added to the signal mixed in the tenth mixing unit );
    A limiter for limiting the amplitude of the signal multiplied by the multiplier and outputting the transient state d-axis current command value (i- e * ds_t);
    The output transient in the limited substate d-axis current command value (i e * ds_t) and the current command value of the speed control section (i * s) of the d-axis current command value (i e * ds) and mixed with the modified d-axis current command value a (i e * ds - m) of the three-phase AC motor.
    [3" claim-type="Currently amended] 3. The method of claim 2,
    The limiter
    Wherein when the transient state d axis current command value (i e * ds_t) is negative, the lower limit value of the transient state d axis current command value is set to zero.
    [4" claim-type="Currently amended] 3. The method of claim 2,
    The limiter
    Wherein when the transient state d axis current command value (i e * ds_t) is positive, the upper limit value of the transient state d axis current command value is limited by the following equation.

    Where I MAX is the maximum permissible current value of the inverter, i eqs is the q-axis current fed back, and i e * ds is the d-axis current command value of the current value (i * s ) of the speed controller.
    [5" claim-type="Currently amended] Detecting an error of the q-axis current by mixing the q-axis current instruction value (i e * qs ) of the current command value (i * s ) and the q-axis current (i eqs );
    Detecting a transient state d-axis current instruction value (i e * ds_t) by multiplying the detected error of the q-axis current by a predetermined gain and a predetermined frequency;
    And outputting the corrected d-axis current instruction value (i e * ds_m) according to the detected transient state d-axis current instruction value (i e * ds_t).
    [6" claim-type="Currently amended] 6. The method of claim 5,
    The step of outputting the corrected d-axis current command value (i e * ds_m)
    Detecting whether the detected transient state d-axis current instruction value (i e * ds_t) is greater than zero;
    Outputting the d-axis current instruction value (i e * ds ) of the current instruction value (i * s ) of the speed control section 20 to the corrected d-axis current instruction value (i e * ds_m) ;
    If the search result is larger than 0, the transient state d-axis current instruction value (i e * ds_t) is the upper limit value of the transient state d-axis current instruction value ) Is greater than a predetermined value, the method further comprising:
    [7" claim-type="Currently amended] The method according to claim 6,
    The step of searching again
    If the search result transient state d-axis current instruction value (i e * ds_t) is higher than the upper limit value of the transient state d-axis current instruction value ) With, if more big less the than the search current command value of the speed control section (i * s) of the d-axis current command value (i e * ds) transients d-axis current command value (i e * ds_t) modify the value obtained by subtracting from the d And outputting it as an axis current command value (i e * ds_m);
    If the search result transient state d-axis current instruction value (i e * ds_t) is higher than the upper limit value of the transient state d-axis current instruction value (I e * ds_m), the lower limit value of the d-axis current for current limitation ( The method of claim 1, further comprising the step of:
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    同族专利:
    公开号 | 公开日
    引用文献:
    公开号 | 申请日 | 公开日 | 申请人 | 专利标题
    法律状态:
    1998-02-26|Application filed by 이종수, 엘지산전 주식회사
    1998-02-26|Priority to KR1019980006197A
    1999-09-15|Publication of KR19990070998A
    优先权:
    申请号 | 申请日 | 专利标题
    KR1019980006197A|KR19990070998A|1998-02-26|1998-02-26|Accelerating current control device and method for three-phase alternating current motor|
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